View TSH310ILT_1329406.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

TSH310
400A High-Speed Operational Amplifier
OptimWattTM device featuring ultra-low consumption, 2mW, and low quiescent current, 400A Bandwidth: 120MHz (Gain=2) Slew rate: 115V/s Specified on 1k Input noise: 7.5nV/Hz Tested on 5V power supply
Pin Connections (top view)
OUT 1 -VCC 2 +IN 3 SOT23-5
5 +VCC
Description
The TSH310 is a very low-power, high-speed operational amplifier. A bandwidth of 120MHz is achieved while drawing only 400A of quiescent current. This low-power characteristic is particularly suitable for high-speed, batterypowered equipment requiring dynamic performance. The TSH310 is a single operator available in SO8 and the tiny SOT23-5 plastic package, saving board space as well as providing excellent thermal performances.
+4 -IN
NC 1 -IN 2 +IN 3 -VCC 4 SO8 _ +
8 NC 7 +VCC 6 OUT 5 NC
Applications
Battery-powered and high-speed systems Communication & video test equipment Portable medical instrumentation ADC drivers
Order Codes
Part Number
TSH310ILT TSH310ID TSH310IDT
Temperature Range
-40C to +85C
Package
SOT23-5 SO-8 SO-8
Conditioning
Tape&Reel Tube Tape&Reel
Marking
K304 TSH310I TSH310I
Note:OptimWattTM is an STMIcroelectronics registered trademark that applies to products with specific features that
optimize energy efficiency.
December 2004
Revision 2
1/19
TSH310
Absolute Maximum Ratings
1 Absolute Maximum Ratings
Table 1: Key parameters and their absolute maximum ratings Symbol
VCC Vid Vin Toper Tstg Tj Rthja Supply Voltage
1
Parameter
Differential Input Voltage2
Value
6 +/-0.5 +/-2.5 -40 to +85 -65 to +150 150 250 150 80 28 500 830 2 0.5 200 60 1.5 1.5 200
Unit
V V V C C C C/W
Input Voltage Operating Free Air Temperature Range Storage Temperature Maximum Junction Temperature Thermal Resistance Junction to Ambient SOT23-5 SO8 Thermal Resistance Junction to Case SOT23-5 SO8 Maximum Power Dissipation4 (@Ta=25C) for Tj=150C SOT23-5 SO8 HBM: Human Body Model 5 (pins 1, 4, 5, 6, 7 and 8) HBM: Human Body Model (pins 2 and 3)
Range3
Rthjc
C/W
Pmax
mW kV kV V V kV kV mA
ESD
MM: Machine Model 6 (pins 1, 4, 5, 6, 7 and 8) MM: Machine Model (pins 2 and 3) CDM: Charged Device Model (pins 1, 4, 5, 6, 7 and 8) CDM: Charged Device Model (pins 2 and 3) Latch-up Immunity
1) All voltages values are measured with respect to the ground pin. 2) Differential voltage are non-inverting input terminal with respect to the inverting input terminal. 3) The magnitude of input and output voltage must never exceed VCC +0.3V. 4) Short-circuits can cause excessive heating. Destructive dissipation can result from short circuit on amplifiers. 5) Human body model, 100pF discharged through a 1.5k resistor into pMin of device. 6) This is a minimum Value. Machine model ESD, a 200pF cap is charged to the specified voltage, then discharged directly into the IC with no external series resistor (internal resistor < 5), into pin to pin of device.
Table 2: Operating conditions Symbol VCC Vicm
Supply Voltage
1
Parameter
Common Mode Input Voltage
Value
4.5 to 5.5 -Vcc+1.5V, +Vcc-1.5V
Unit
V V
1) Tested in full production at 5V (2.5V) supply voltage.
2/19
Electrical Characteristics
TSH310
2 Electrical Characteristics
Table 3: Electrical characteristics for VCC = 2.5Volts, Tamb = 25C (unless otherwise specified) Symbol DC performance
Vio Input Offset Voltage Offset Voltage between both inputs Vio drift vs. Temperature Tamb Tmin. < Tamb < Tmax. Tmin. < Tamb < Tmax. 1.7 2.1 4 3.1 3.5 0.1 0.3 -57 -65 -61 -59 -82 -79 -50 46 400 530 5 12 6.5 mV
Parameter
Test Condition
Min.
Typ.
Max.
Unit
Vio
Iib+ IibCMR SVR
V/C A A
dB dB
Non Inverting Input Bias Current Tamb DC current necessary to bias the input + Tmin. < Tamb < Tmax. Inverting Input Bias Current Tamb DC current necessary to bias the input Tmin. < Tamb < Tmax. Common Mode Rejection Ratio 20 log (Vic/Vio ) Supply Voltage Rejection Ratio 20 log (Vcc/Vio) Power Supply Rejection Ratio 20 log (Vcc/Vout) Positive Supply Current DC consumption with no input signal Transimpedance Output Voltage/Input Current Gain in open loop of a CFA. For a VFA, the analog of this feature is the Open Loop Gain (AVD) -3dB Bandwidth Frequency where the gain is 3dB below the DC gain AV Note: Gain Bandwidth Product criterion is not applicable for Current-FeedbackAmplifiers
Vic = 1V
Tmin. < Tamb < Tmax.
Vcc= 3.5V to 5V
Tmin. < Tamb < Tmax. AV = +1, Vcc=100mV at 1kHz Tmin. < Tamb < Tmax. No load
PSR
dB
ICC
A
Dynamic performance and output characteristics
RL = 1k,Vout = 1V Tmin. < Tamb < Tmax. 1.36 Small Signal Vout=20mVp-p RL = 1k AV = +1, Rfb = 3k AV = +2, Rfb = 3k AV = +10, Rfb = 510 M 0.6 1.45 M
ROL
Bw
80
230 120 26 25
MHz
Gain Flatness @ 0.1dB Small Signal Vout=20mVp-p Band of frequency where the gain varia- AV = +2, RL = 1k tion does not exceed 0.1dB SR Slew Rate Maximum output speed of sweep in large signal High Level Output Voltage Low Level Output Voltage Vout = 2Vp-p, AV = +2, RL = 1k RL = 1k Tmin. < Tamb < Tmax. RL = 1k Tmin. < Tamb < Tmax. 75 1.55
115 1.65 1.58 -1.66 -1.60 -1.55
V/s V V
VOH VOL
3/19
TSH310
Electrical Characteristics
Table 3: Electrical characteristics for VCC = 2.5Volts, Tamb = 25C (unless otherwise specified) Symbol
Iout
Parameter
Isink Short-circuit Output current coming in the op-amp. See fig-8 for more details Isource Output current coming out from the opamp. See fig-11 for more details
Test Condition
Output to GND Tmin. < Tamb < Tmax. Output to GND Tmin. < Tamb < Tmax.
Min.
70
Typ.
110 100
Max.
Unit
60
100 85
mA
Noise and distortion
eN Equivalent Input Noise Voltage see application note on page 13 Equivalent Input Noise Current (+) see application note on page 13 Equivalent Input Noise Current (-) see application note on page 13 Spurious Free Dynamic Range The highest harmonic of the output spectrum when injecting a filtered sine wave F = 100kHz F = 100kHz F = 100kHz Vout = 2Vp-p, AV = +2, RL = 1k F = 1MHz F = 10MHz 7.5 13 6 nV/Hz pA/Hz pA/Hz
iN
SFDR
-87 -55
dBc dBc
Table 4: Closed-loop gain and feedback components VCC (V) Gain
+10 -10 +2 2.5 -2 +1 -1 1.5k 3k 1.3k 80 210 120 10 5 60
Rfb ()
510 510 3k
-3dB Bw (MHz)
26 23 120
0.1dB Bw (MHz)
4 4 6
4/19
Electrical Characteristics
Figure 1: Frequency Response, positive Gain
24 22 20 18 16 14
TSH310
Figure 4: Frequency response, negative gain
24 22 20 18 16 14
Gain=+10
Gain=-10
Gain=+4
Gain=-4
Gain (dB)
Gain=+2
Gain (dB)
12 10 8 6 4 2 0 -2 -4 -6 -8
12 10 8 6 4 2 0 -2 -4 -6 -8
Gain=-2
Gain=+1
Gain=-1
-10 1M
Small Signal Vcc=5V Load=1k
10M 100M
-10 1M
Small Signal Vcc=5V Load=1k
10M 100M
Frequency (Hz)
Frequency (Hz)
Figure 2: Gain Flatness, gain=+4
12,1
Figure 5: Gain flatness, gain=+2
6,2 6,1
12,0
6,0 5,9
Gain Flatness (dB)
Gain Flatness (dB)
11,9
5,8 5,7 5,6 5,5 5,4 5,3 5,2 5,1 5,0 1M
11,8
11,7
11,6
Gain=+4 Small Signal Vcc=5V Load=1k
10M 100M
Gain=+2 Small Signal Vcc=5V Load=1k
10M 100M
11,5 1M
Frequency (Hz)
Frequency (Hz)
Figure 3: Frequency response vs. capa-load
10 8 6 C-Load=10pF R-iso=0
Figure 6: Step response vs. capa-load
3
2 C-Load=1pF R-iso=0
C-Load=1pF, 10pF and 22pF
2 0 -2 -4 -6 -8 -10 1M
Vin
+ -
Output step (Volt)
4
Gain (dB)
1
Vin
+ -
Vout R-iso 3k 1k C-Load
C-Load=22pF R-iso=47ohms
Vout
3k
0
3k 3k C-Load
1k
Gain=+2, Vcc=5V, Small Signal
Gain=+2, Vcc=5V, Small Signal
10M
100M
-1 0,0
5,0n
10,0n
15,0n
20,0n
25,0n
30,0n
Frequency (Hz)
Time (ns)
5/19
TSH310
Figure 7: Slew rate
Electrical Characteristics
Figure 10: Quiescent current vs. Vcc
2,0
400
Icc(+)
Output Response (V)
1,5
200
Icc (micro-A)
1,0
0
Gain=+2 Vcc=5V Inputs to ground, no load
0,5
-200
0,0 -10ns -5ns 0s 5ns 10ns
Gain=+2 Vcc=5V Load=1k
15ns 20ns
Icc(-)
-400
1,25
1,50
1,75
2,00
2,25
2,50
Time (ns)
+/-Vcc (V)
Figure 8: Isink
150
+2.5V VOL
Figure 11: Isource
0
+
without load
125
-1V
_
- 2.5V
Isink V
-25
Isink (mA)
Amplifier in open loop without load
Isource (mA)
100
RG
-50
75
-75
+
+2.5V VOH
without load
50
-100
+1V
_
- 2.5V
Isource V
25
-125
RG
Amplifier in open loop without load
0 -2,0
-1,5
-1,0
-0,5
0,0
-150 0,0
0,5
1,0
1,5
2,0
V (V)
V (V)
Figure 9: Output amplitude vs. load
4,0
Figure 12: Input voltage noise vs. frequency
10,0
Max. Output Amplitude (Vp-p)
9,5
3,5
9,0
Gain=32dB Rg=12ohms Rfb=510ohms non-inverting input in short-circuit Vcc=5V
en (nV/VHz)
Gain=+2 Vcc=5V Load=1k
3,0
8,5
8,0
2,5
7,5
2,0 10 100 1k 10k 100k
7,0 100
1k
10k
100k
1M
10M
100M
Load (ohms)
Frequency (Hz)
6/19
Electrical Characteristics
Figure 13: Distortion vs. output amplitude
-20 -25 -30 -35
64
TSH310
Figure 16: CMR vs. temperature
66
HD2 & HD3 (dBc)
-40 -45 -50 -55 -60 -65 -70 -75 -80 0
CMR (dB)
Gain=+2 Vcc=5V F=10MHz Load=1k
1 2 3 4
HD2
62
60
HD3
58
Gain=+1 Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
56
Output Amplitude (Vp-p)
Temperature (C)
Figure 14: Output amplitude vs. frequency
5
Figure 17: SVR vs. temperature
90
4 85
Vout max. (Vp-p)
SVR (dB)
3
80
2
75 1
0 100k
Gain=+2 Vcc=5V Load=1k
1M 10M 100M 70
Gain=+1 Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
Frequency (Hz)
Temperature (C)
Figure 15: Bandwidth vs. temperature
200 190 180 170 160
Figure 18: Slew-Rate vs. temperature
140
130
neg. SR
SR (V/micro-s)
120
Bw (MHz)
pos. SR
110
150 140 130 120 110 100 90 -40 -20 0 20 40 60 80 100 120
100
Gain=+1 Vcc=5V Load=100
90
Gain=+1 Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
80
Temperature (C)
Temperature (C)
7/19
TSH310
Figure 19: ROL vs. temperature
1,60
Electrical Characteristics
Figure 22: VOH & VOL vs. temperature
2
1,55 1,50 1,45
1
VOH
1,40 1,35 1,30 1,25 1,20 -40 -20 0 20 40 60 80 100 120
VOH & OL (V)
ROL (M)
0
-1
VOL
-2
-3
Open Loop Vcc=5V
Gain=+1 Vcc=5V Load=100
-20 0 20 40 60 80
-4 -40
Temperature (C)
Temperature (C)
Figure 20: I-bias vs. temperature
3
Figure 23: Icc vs. temperature
400
2
Ib(+)
Icc(+)
200 0
1
ICC (micro A)
IBIAS (A)
-200
0
Ib(-)
Icc(-)
-400
-1
-600
-2
Gain=+1 Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
-800
Gain=+1 Vcc=5V no Load in(+) and in(-) to GND
-40 -20 0 20 40 60 80 100 120
-3
-1000
Temperature (C)
Temperature (C)
Figure 21: Vio vs. temperature
2,0
Figure 24: Iout vs. temperature
200 150 100
1,8
1,6
Isource
50
Iout (mA)
VIO (mV)
1,4
0 -50
1,2
Isink
-100 -150
1,0
0,8
0,6
Open Loop Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
-200 -250 -300
Output: short-circuit Gain=+1 Vcc=5V
-40 -20 0 20 40 60 80 100 120
Temperature (C)
Temperature (C)
8/19
Evaluation Boards
TSH310
3 Evaluation Boards
An evaluation board kit optimized for high-speed operational amplifiers is available (order code: KITHSEVAL/STDL). The kit includes the following evaluation boards, as well as a CD-ROM containing datasheets, articles, application notes and a user manual:
l SOT23_SINGLE_HF BOARD: Board for the evaluation of a single high-speed op-amp in SOT23-5
package.
l SO8_SINGLE_HF: Board for the evaluation of a single high-speed op-amp in SO8 package. l SO8_DUAL_HF: Board for the evaluation of a dual high-speed op-amp in SO8 package. l SO8_S_MULTI: Board for the evaluation of a single high-speed op-amp in SO8 package in inverting
and non-inverting configuration, dual and single supply.
l SO14_TRIPLE: Board for the evaluation of a triple high-speed op-amp in SO14 package with video
application considerations.
Board material:
l 2 layers l FR4 (r=4.6) l epoxy 1.6mm l copper thickness: 35m
Figure 25: Evaluation kit for high-speed op-amps
9/19
TSH310
Power Supply Considerations
4 Power Supply Considerations
Correct power supply bypassing is very important for optimizing performance in high-frequency ranges. Bypass capacitors should be placed as close as possible to the IC pins to improve high-frequency bypassing. A capacitor greater than 1F is necessary to minimize the distortion. For better quality bypassing, a capacitor of 10nF can be added using the same implementation conditions. Bypass capacitors must be incorporated for both the negative and the positive supply. For example: on the SO8_SINGLE_HF board, these capacitors are C6, C7, C8, C9. Figure 26: Circuit for power supply bypassing
+VCC + 10nF
10microF
+ 10nF
10microF + -VCC
Single power supply
In the event that a single supply system is used, new biasing is necessary to assume a positive output dynamic range between 0V and +VCC supply rails. Considering the values of VOH and VOL, the amplifier will provide an output dynamic from +0.9V to +4.1V on 1k load. The amplifier must be biased with a mid-supply (nominally +VCC/2), in order to maintain the DC component of the signal at this value. Several options are possible to provide this bias supply, such as a virtual ground using an operational amplifier or a two-resistance divider (which is the cheapest solution). A high resistance value is required to limit the current consumption. On the other hand, the current must be high enough to bias the non-inverting input of the amplifier. If we consider this bias current (55A max.) as the 1% of the current through the resistance divider to keep a stable mid-supply, two resistances of 470 can be used. The input provides a high pass filter with a break frequency below 10Hz which is necessary to remove the original 0 volt DC component of the input signal, and to fix it at +VCC/2. Figure 27 illustrates a 5V single power supply configuration for the SO8_SINGLE evaluation board (see Evaluation Boards on page 9).
10/19
Power Supply Considerations
TSH310
A capacitor CG is added in the gain network to ensure a unity gain in low frequency to keep the right DC component at the ouput. CG contributes to a high-pass filter with Rfb//RG and its value is calculated with a consideration of the cut-off frequency of this low-pass filter. Figure 27: Circuit for +5V single supply
+5V 10F IN +5V R1 470 Rfb R2 470 RG + 1F 10nF + CG Rin 1k
+
_
OUT
1k
11/19
TSH310
Noise Measurements
5 Noise Measurements
The noise model is shown in Figure 28, where:
l eN: input voltage noise of the amplifier l iNn: negative input current noise of the amplifier l iNp: positive input current noise of the amplifier
Figure 28: Noise model
+
R3
iN+
_
output HP3577 Input noise: 8nV/Hz
N3
iN-
eN
N2
R1
R2
N1
The thermal noise of a resistance R is:
4kTRF
where F is the specified bandwidth. On a 1Hz bandwidth the thermal noise is reduced to
4kTR
where k is the Boltzmann's constant, equal to 1,374.10-23J/K. T is the temperature (K). The output noise eNo is calculated using the Superposition Theorem. However eNo is not the simple sum of all noise sources, but rather the square root of the sum of the square of each noise source, as shown in Equation 1:
eNo = 2 2 2 2 2 2 V 1 + V2 + V3 + V4 + V5 + V6
Equation 1
eNo
2
2 2 2 2 2 2 2 = eN x g + iNn x R2 + iNp x R3 x g
------+ R2 R1
2
2 x 4kTR1 + 4kTR2 + 1 + R2 x 4kTR3 ------R1
Equation 2
12/19
Noise Measurements
TSH310
The input noise of the instrumentation must be extracted from the measured noise value. The real output noise value of the driver is:
eNo = 2 2 ( Measured ) - ( instrumentation )
Equation 3
The input noise is called the Equivalent Input Noise as it is not directly measured but is evaluated from the measurement of the output divided by the closed loop gain (eNo/g). After simplification of the fourth and the fifth term of Equation 2 we obtain:
eNo
2
2 2 2 2 2 2 2 = eN x g + iNn x R2 + iNp x R3 x g
+ g x 4k TR2 + 1 + R2 -----R1
2
x 4kTR3
Equation 4
Measurement of the input voltage noise eN
If we assume a short-circuit on the non-inverting input (R3=0), from Equation 4 we can derive:
eNo =
2 2 2 2 eN x g + iNn x R 2 + g x 4kTR 2
Equation 5
In order to easily extract the value of eN, the resistance R2 will be chosen to be as low as possible. In the other hand, the gain must be large enough: R3=0, gain: g=100
Measurement of the negative input current noise iNn
To measure the negative input current noise iNn, we set R3=0 and use Equation 5. This time the gain must be lower in order to decrease the thermal noise contribution: R3=0, gain: g=10
Measurement of the positive input current noise iNp
To extract iNp from Equation 3, a resistance R3 is connected to the non-inverting input. The value of R3 must be chosen in order to keep its thermal noise contribution as low as possible against the iNp contribution: R3=100, gain: g=10
13/19
TSH310
Intermodulation Distortion Product
6 Intermodulation Distortion Product
The non-ideal output of the amplifier can be described by the following series:
2 n Vout = C + C V + C V in + ...C V in 0 1 in 2 n
due to non-linearity in the input-output amplitude transfer, where the input is Vin=Asint, C0 is the DC component, C1(Vin) is the fundamental and Cn is the amplitude of the harmonics of the output signal Vout. A one-frequency (one-tone) input signal contributes to harmonic distortion. A two-tone input signal contributes to harmonic distortion and to the intermodulation product. The study of the intermodulation and distortion for a two-tone input signal is the first step in characterizing the driving capability of multi-tone input signals. In this case:
V in = A sin t + A sin t 1 2
then:
V out = C + C ( A sin t + A sin t ) + C ( A sin t + A sin t ) 1 2 1 2 2 0 1 2
... + C n ( A sin 1 t + A sin 2 t )
n
From this expression, we can extract the distortion terms, and the intermodulation terms form a single sine wave: second-order intermodulation terms IM2 by the frequencies (1-2) and (1+2) with an amplitude of C2A2 and third-order intermodulation terms IM3 by the frequencies (21-2), (21+2), (- 1+22) and (1+22) with an amplitude of (3/4)C3A3. The measurement of the intermodulation product of the driver is achieved by using the driver as a mixer by a summing amplifier configuration (see Figure 29). In this way, the non-linearity problem of an external mixing device is avoided. Figure 29: Inverting summing amplifier (using evaluation board SO8_S_MULTI)
Vin1 Vin2
R1
Rfb
R2
_
Vout
+
1k
R
14/19
The Bias of an Inverting Amplifier
TSH310
7 The Bias of an Inverting Amplifier
A resistance is necessary to achieve a good input biasing, such as resistance R shown in Figure 30. The magnitude of this resistance is calculated by assuming the negative and positive input bias current. The aim is to compensate for the offset bias current, which could affect the input offset voltage and the output DC component. Assuming Ib-, Ib+, Rin, Rfb and a zero volt output, the resistance R will be:
R in x R fb R = ---------------------R in + R fb
Figure 30: Compensation of the input bias current
Rfb
Ib-
Rin
_
Vcc+ Output
+
Ib+ R Vcc-
Load
15/19
TSH310
Active Filtering
8 Active Filtering
Figure 31: Low-pass active filtering, Sallen-Key
C1
R1 IN
R2 C2
+
OUT
_
1k
Rfb RG
From the resistors Rfb and RG we can directly calculate the gain of the filter in a classical non-inverting amplification configuration:
A R fb = g = 1 + --------V R g
We assume the following expression as the response of the system:
T Vout g j = ------------------- = --------------------------------------------j Vin 2 j j ( j ) 1 + 2 ------ + ------------c 2 c
The cut-off frequency is not gain-dependent and so becomes:
1 c = ------------------------------------R1 R2C1C2
The damping factor is calculated by the following expression:
1 = -- ( C R + C R + C R - C R g ) 12 21 11 2c 11
The higher the gain, the more sensitive the damping factor is. When the gain is higher than 1, it is preferable to use some very stable resistor and capacitor values. In the case of R1=R2=R:
R fb 2C2 - C --------1R g = -----------------------------------2CC 12
Due to a limited selection of values of capacitors in comparison with resistors, we can fix C1=C2=C, so that:
R fb 2R2 - R --------1R g = -----------------------------------2RR 12
16/19
Package Mechanical Data
TSH310
9 Package Mechanical Data
SOT23-5L MECHANICAL DATA
mm. DIM. MIN. A A1 A2 b C D E E1 e e1 L 0.35 0.90 0.00 0.90 0.35 0.09 2.80 2.60 1.50 0 .95 1.9 0.55 13.7 TYP MAX. 1.45 0.15 1.30 0.50 0.20 3.00 3.00 1.75 MIN. 35.4 0.0 35.4 13.7 3.5 110.2 102.3 59.0 37.4 74.8 21.6 TYP. MAX. 57.1 5.9 51.2 19.7 7.8 118.1 118.1 68.8 mils
17/19
TSH310
Package Mechanical Data
SO-8 MECHANICAL DATA
DIM. A A1 A2 B C D E e H h L k ddd 0.1 5.80 0.25 0.40 mm. MIN. 1.35 0.10 1.10 0.33 0.19 4.80 3.80 1.27 6.20 0.50 1.27 8 (max.) 0.04 0.228 0.010 0.016 TYP MAX. 1.75 0.25 1.65 0.51 0.25 5.00 4.00 MIN. 0.053 0.04 0.043 0.013 0.007 0.189 0.150 0.050 0.244 0.020 0.050 inch TYP. MAX. 0.069 0.010 0.065 0.020 0.010 0.197 0.157
0016023/C
18/19
Revision History
TSH310
10 Revision History
Date 01 Oct 2004 December 2004 Revision 1 2 Description of Changes First release corresponding to Preliminary Data version of datasheet. Release of mature product datasheet.
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. The ST logo is a registered trademark of STMicroelectronics All other names are the property of their respective owners (c) 2004 STMicroelectronics - All rights reserved
STMicroelectronics group of companies Australia - Belgium - Brazil - Canada - China - Czech Repubic - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan Malaysia - Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States of America www.st.com
19/19

▲Up To Search▲

Price & Availability of TSH310ILT

	To Download TSH310ILT Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .